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AD8339 데이터시트(PDF) 11 Page - Analog Devices |
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AD8339 데이터시트(HTML) 11 Page - Analog Devices |
11 / 15 page Preliminary Technical Data AD8339 Rev. PrA | Page 11 of 15 current mirror. An external transimpedance amplifier is needed to convert the I and Q outputs to voltages. Table 4. Phase Select Code for Channel-to-Channel Phase Shift φ-Shift PHx3 (MSB) PHx2 PHx1 PHx0 (LSB) 0º 0 0 0 0 22.5º 0 0 0 1 45º 0 0 1 0 67.5º 0 0 1 1 90º 0 1 0 0 112.5º 0 1 0 1 135º 0 1 1 0 157.5º 0 1 1 1 180º 1 0 0 0 202.5º 1 0 0 1 225º 1 0 1 0 247.5º 1 0 1 1 270º 1 1 0 0 292.5º 1 1 0 1 315º 1 1 1 0 337.5º 1 1 1 1 DYNAMIC RANGE AND NOISE Figure 2 is an interconnection block diagram of two channels (1/2 of the AD8339), more channels are easily added to the summation (up to 16 when using an AD8021 as the summation amplifier) by wire-or connecting the outputs as shown for two channels. For optimum system noise performance, the RF input signal is provided by a very low noise amplifier such as the LNA of the AD8332/AD8334 or the preamplifier of the AD8335. In beamformer applications, the I and Q outputs of a number of receiver channels are summed (for example, the two channels illustrated in Figure 2). The dynamic range of the system increases by the factor 10log10(N), where N is the number of channels (assuming random uncorrelated noise.) The noise in the two channel example of Figure 2 is increased by 3 dB while the signal doubles (+6 dB), yielding an aggregate SNR improvement of (+6 − 3) = +3 dB. For four channels the dynamic range will increase by +6 dB and so on. Judicious selection of the RF amplifier ensures the least degradation in dynamic range. The input referred spectral voltage noise density (en) of the AD8339 is nominally about TBD nV/√Hz. For the noise of the AD8339 to degrade the system noise figure (NF) by 1 dB, the combined noise of the source and the LNA should be about twice that of the AD8339 or TBD nV/√Hz. If the noise of the circuitry before the AD8339 is less than TBD nV/√Hz then the system NF degrades more than 1 dB. For example, if the noise contribution of the LNA and source is equal to the AD8339, or TBD nV/√Hz, the degradation is 3 dB. If the circuit noise preceding the AD8339 is 1.3× as large as that of the AD8339 (or about TBD nV/√Hz) the degradation is 2 dB. For a circuit noise 1.45× that of the AD8339 (TBD nV/√Hz) the degradation is 1.5 dB. To determine the input referred noise it is important to know the active low pass filter (LPF) values RFILT and CFILT, shown in Figure 2. Typical filter values for a single channel are 1.58 kΩ and 1 nF, and implement a 100 kHz single-pole LPF. In the case that two channels are summed as is done on the evaluation board, the values would be the same as for a single channel of the AD8333, namely 787 Ω and 2.2 nF. If the RF and LO are offset by 10 kHz, the demodulated signal is 10 kHz and is passed by the LPF. The single-channel mixing gain, from the RF input to the AD8021 output (for example, I1´, Q1´) is approximately 1.7 (4.7 dB). This together with the TBD nV/√Hz of AD8339 noise results in about TBD nV/√Hz at the AD8021 output. Since the AD8021, including the 1.58 kΩ feedback resistor, contributes another 6.3 nV/√Hz, the total output referred noise is about TBD nV/√Hz. This value can be adjusted by increasing the filter resistor while maintaining the corner frequency, thereby increasing the gain. The factor limiting the magnitude of the gain is the output swing and drive capability of the op-amp selected for the I-to-V converter, in this instance the AD8021. Because any amplifier has limited drive capability there will be a finite number of channels that can be summed. This is explained in great detail in the section below called – Channel Summing. |
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