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LM25010 데이터시트(PDF) 9 Page - Texas Instruments |
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LM25010 데이터시트(HTML) 9 Page - Texas Instruments |
9 / 31 page FS = VOUT 2 x L1 x 1.4 x 1020 RL x RON 2 DC = tON tON + tOFF VOUT VIN = tON x FS = FS = VOUT x (VIN ± 1.4V) 1.18 x 10 -10 x (RON + 1.4 k:) x VIN 9 LM25010, LM25010-Q1 www.ti.com SNVS419E – DECEMBER 2005 – REVISED MAY 2016 Product Folder Links: LM25010 LM25010-Q1 Submit Documentation Feedback Copyright © 2005–2016, Texas Instruments Incorporated Feature Description (continued) The LM25010 requires a minimum of 25-mV of ripple voltage at the FB pin for stable fixed-frequency operation. If the output capacitor’s ESR is insufficient, additional series resistance may be required (R3 in the Functional Block Diagram). The LM25010 operates in continuous conduction mode at heavy load currents, and discontinuous conduction mode at light load currents. In continuous conduction mode current always flows through the inductor, never decaying to zero during the OFF-time. In this mode the operating frequency remains relatively constant with load and line variations. The minimum load current for continuous conduction mode is one-half the inductor’s ripple current amplitude. Calculate the operating frequency in the continuous conduction mode with Equation 2. (2) The buck switch duty cycle is equal to Equation 3. (3) Under light load conditions, the LM25010 operates in discontinuous conduction mode, with zero current flowing through the inductor for a portion of the OFF-time. The operating frequency is always lower than that of the continuous conduction mode, and the switching frequency varies with load current. Conversion efficiency is maintained at a relatively high level at light loads because the switching losses diminish as the power delivered to the load is reduced. Calculate the approximate discontinuous mode operating frequency with Equation 4. where • RL = the load resistance (4) 7.3.2 Start-Up Regulator (VCC) A high voltage bias regulator is integrated within the LM25010. The input pin (VIN) can be connected directly to line voltages between 6 V and 42 V. Referring to the Functional Block Diagram and the graph of VCC vs VIN, when VIN is between 6 V and the bypass threshold (nominally 8.9 V), the bypass switch (Q2) is on, and VCC tracks VIN within 100 mV to 150 mV. The bypass switch on-resistance is approximately 50 Ω, with inherent current limiting at approximately 100 mA. When VIN is above the bypass threshold, Q2 is turned off, and VCC is regulated at 7 V. The VCC regulator output current is limited at approximately 15 mA. When the LM25010 is shutdown using the RON/SD pin, the VCC bypass switch is shut off, regardless of the voltage at VIN. When VIN exceeds the bypass threshold, the time required for Q2 to shut off is approximately 2 µs to 3 µs. The capacitor at VCC (C3) must be a minimum of 0.47 µF to prevent the voltage at VCC from rising above its absolute maximum rating in response to a step input applied at VIN. C3 must be located as close as possible to the LM25010 pins. In applications with a relatively high input voltage, power dissipation in the bias regulator is a concern. An auxiliary voltage of between 7.5 V and 14 V can be diode connected to the VCC pin (D2 in Figure 8) to shut off the VCC regulator, reducing internal power dissipation. The current required into the VCC pin is shown in the Typical Performance Characteristics. Internally a diode connects VCC to VIN requiring that the auxiliary voltage be less than VIN. The turn-on sequence is shown in Figure 1. When VCC exceeds the undervoltage lockout threshold (UVLO) of 5.25 V (t1 in Figure 1), the buck switch is enabled, and the SS pin is released to allow the softstart capacitor (C6) to charge up. The output voltage VOUT is regulated at a reduced level which increases to the desired value as the softstart voltage increases (t2 in Figure 1). |
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